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UTC1062A
LI NEAR I NTEGRATED CI RCUI T
LOW VOLTAGE TELEPHONE TRANSMISSION CIRCUIT WITH DIALLER INTERFACE
DESCRIPTION
The UTC1062A is a bipolar integrated circuit per- forming all speech and line interface function required in the fully electronic telephone sets. It performs electronic switching between dialing speech. The circuit is able to operate down to d.c. line voltage of 1.6v (with reduced performance) to facilitate the use of more telephone sets in parallel.
FEATURES
* Low d.c. line voltage; operates down to 1.6V (excluding polarity guard) * Voltage regulator with adjustment static resistance * Provides supply with limited current for external circuitry * Symmetrical high-impedance inputs (64k for dynamic, magnetic or piezoelectric microphones * Asymmetrical high-impedance inputs (32k for electric microphones * DTMF signal input with confidence tone * Mute input for pulse or DTMF dialing * Receiving amplifier for several types of earphones * Large amplification setting range on microphone and ear piece amplifiers * Line loss compensation facility, line current dependent (microphone and ear piece amplifiers) * Gain control adaptable to exchange supply * Possibility to adjust the d.c. line voltage
DIP-16
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Line voltage at Iline=15mA Line current operating range[pin1] normal operation with reduced performance Internal supply current Supply current for peripherals at Iline=15 mA mute input HIGH Vcc>2.2V Vcc>2.8V Voltage amplification range microphone amplifier receiving amplifier Line loss compensation Amplification control range Exchange supply voltage range Exchange feeding bridge resistance range Operating ambient temperature range
VLN Iline Iline ICC
typ.
3.8 V 11 to 140 mA 1 to 11 mA 1mA
typ.
Ip Ip AVD AVD AVD Vexch Rexch Tamb
typ. typ.
1.8mA 0.7mA 44 to 52 dB 20 to 39 dB
Typ.
6 dB 36 to 60V 400 to 1000 -25 to +75C
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QUICK REFERENCE DATA
UTC1062A
VCC 13
LI NEAR I NTEGRATED CI RCUI T
LN 1 5 GAR
IR 10 4 OR
MIC+ 7 MIC- 6
2 GAS1
3 GAS2 DTMF 11
dB
MUTE 12 SUPPLY AND REFERENCE CONTROL CURRENT CURRENT REFERENCE 9 VEE 14 REG 15 AGC 8 STAB 16 SLPE LOW VOLTAGE CIRCUIT
Fig.1 Block Diagram
1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 LN GAS1 GAS2 OR GAR MICMIC+ STAB VEE IR DTMF MUTE Vcc REG AGC SLPE positive line terminal gain adjustment; transmitting amplifier gain adjustment; transmitting amplifier non-inverting output, receiving amplifier gain adjustment; receiving amplifier inverting microphone input non-inverting microphone input current stabilizer negative line terminal receiving amplifier input dual-tone multi-frequency input mute input positive supply decoupling voltage regulator decoupling automatic gain control input slope (DC resistance) adjustment
LN
1
16
SLPE AGC
GAS1 GAS2
2
15
3
14
REG
OR
4
13
VCC
GAR
5
12
MUTE
MIC-
6
11
DTMF
MIC+
7
10
IR
STAB
8
9
VEE
Fig.2 Pining Diagram
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UTC1062A
parameter
Positive continuous line voltage Repetitive line voltage during switch-on or line interruption Repetitive peak line voltage for a 1 ms pulse/5s
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conditions symbol
VLN VLN R10=13 R9=20 (see Fig.15) R9=20
RATING LIMITING VALUES (In accordance with the Absolute Maximum System)
min. max.
12 13.2
unit
V V
28 V VLN 140 mA Iline VCC 0.7 V Vi Vi 0.7 V R9=20 640 mW Total power dissipation(2) Ptot 40 125 C Storage temperature range Tstg 25 75 C Operating ambient temperature range Tamb 125 C Junction temperature Tj 1. Mostly dependent on the maximum required Tamb and the voltage between LN and SLPE (see Figs 6). 2. Calculated for the maximum ambient temperature specified Tamb=75 C and a maximum junction temperature of 125C. Line current (1) Voltage on all other pins
THERMAL RESISTANCE
From junction to ambient in free air Rth j-a = 75K/W
ELECTRONICAL CHARACTERISTICS
(Iline=11 to 140mA;VEE=0V;f=800Hz;Tamb=25C;unless otherwise specified)
parameter Supply; LN and VCC(pins 1 and 13)
Voltage drop over circuit, between LN and VEE
conditions
symbol
min.
typ.
max.
unit
Variation with temperature Voltage drop over circuit, between LN and VEE with external resistor RVA
MIC inputs open Iline=1mA Iline=4mA Iline=15mA Iline=100mA Iline=140mA Iline=15mA Iline=15mA RVA(LN to REG) =68k Iline=15mA RVA(REG to SLPE) =39k VCC=2.8V Iline=15mA MUTE=HIGH Ip=1.2mA lp=0mA
VLN VLN VLN VLN VLN VLN/T
3.55 4.9
1.6 1.9 4.0 5.7 0.3
4.25 6.5 7.5
V V V V V mV/K
3.5
V
4.5 ICC 0.9 1.35
V mA
Supply current Supply voltage available for peripheral circuitry
VCC VCC
2.2
2.7 3.4
V V
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UTC1062A
LI NEAR I NTEGRATED CI RCUI T
symbol min. typ. max. unit
ELECTRONICAL CHARACTERISTICS (continued)
parameter conditions Microphone inputs MIC+ and MIC- (pins6 and 7)
Input impedance (differential) between MIC- and MIC+ Input impedance (sigle-ended) MIC- or MIC+ to VEE Common mode rejection ratio Voltage gain MIC+ or MIC- to LN Gain variation with frequency at f=300Hz and f=3400Hz Gain variation with temperature At25C and +75C
Zi Zi kCMR Iline=15mA R7=68k w.r.t.800Hz w.r.t.25C without R6; Iline=50mA
64 32 82
k k dB
Gv Gvf
54
56 0.2
58
dB dB
GvT
0.2
dB
Dual-tone multi-frequency
input DTMF (pin 11) Input impedance Voltage gain from DTMF to LN Gain variation with frequency at f=300Hz and f=3400Hz Gain variation with temperature At25C and +75C Zi Iline=15mA R7=68k w.r.t.800Hz w.r.t.25C Iline=50mA Gv Gvf 24.0 20.7 25.5 0.2 27.0 k dB dB
GvT
0.2
dB
Gain adjustment GAS1 and GAS2 (pin2 and 3)
Gain variation of the transmitting amplifier by varying R7 between GAS1 and GAS2 Sending amplifier output LN(pin 1) Output voltage
Gv Iline=15mA THD=10% Iline=4mA THD=10% Iline=15mA; R7=68k; 200 between MIC- and MIC+; psophometrically weighted
8
0
dB
VLN(rms) VLN(rms)
1.7
2.3 0.8
V V
Noise output voltage
VNO(rms) Zi
69 21
dB k
Receiving amplifier input IR (pin10)
Input impedance
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UTC1062A
parameter Receiving amplifier output OR (pin4)
Output impedance Voltage gain from IR to OR
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conditions symbol
Zo Iline=15mA; RL(from pin 9 to pin 4 )=300 w.r.t.800Hz w.r.t.25C without R6 Iline=50mA sine wave drive; Ip=0mA;THD=2% R4=100k Iline=15mA RL=450 RL=600 THD=10% R4=100k RL=150 Iline=4mA Iline=15mA R4=100k IR open-circuit psophometrically weighted RL=300
ELECTRONICAL CHARACTERISTICS (continued)
min. typ.
4
max.
unit
Gv Gvf
29
30 0.2
32
dB dB
Gain variation with frequency at f=300Hz and f=3400Hz Gain variation with temperature At25C and +75C
GvT
0.2
dB
Output voltage
VO(rms) VO(rms)
0.22 0.3
0.33 0.48
V V
Output voltage
VO(rms)
15
mV
Noise output voltage
VNO(rms)
50
V
Gain adjustment GAR(pin 5)
Gain variation of receiving amplifier achievable by varying R4 between GAR and OR
Gv VIH VIL IMUTE MUTE=HIGH MUTE=HIGH R4=100k RL=300 Gv
11 1.5 8 70
0 VCC 0.3 15
dB V V A dB
MUTE input (pin 12)
Input voltage(HIGH) Input voltage(LOW) Input current
Reduction of gain
MIC+ or MIC to OR Voltage gain from DTMF to OR
Gv
19
dB
Automatic gain control input AGC pin(15)
Controlling the gain from lR to OR and the gain from MIC+/MICto LN;R6 between AGC and VEE Gain control range
R6=110k Iline=70mA
Gv
5.8
dB
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UTC1062A
parameter
Highest line current for maximum gain Minimum line current for minimum gain
LI NEAR I NTEGRATED CI RCUI T
conditions symbol
Iline Iline
ELECTRONICAL CHARACTERISTICS (continued)
min. typ.
23 61
max.
unit
mA mA
FUNCTIONAL DESCRIPTION
Supply: VCC,LN,SLPE,REG and STAB
Power for the UTC1062A and its peripheral circuits is usually obtained from the telephone line. The IC supply voltage is derived from the line via a dropping resistor and regulated by the UTC1062A,The supply voltage Vcc may also be used to supply external circuits e.g. dialing and control circuits. Decoupling of the supply voltage is performed by a capacitor between Vcc and VEE while the internal voltage regulator is decoupled by a capacitor between REG and VEE. The DC current drawn by the device will vary in accordance with varying values of the exchange voltage(Vexch), the feeding bridge resistance(Rexch) and the DC resistance of the telephone line(Rline). The UTC1062A has an internal current stabilizer operating at a level determined by a 3.6k resistor connected between STAB and VEE(see Fig.8). When the line current(Iline) is more than 0.5 mA greater than the sum of the IC supply current ( Icc) and the current drawn by the peripheral circuitry connected to VCC(lp) the excess current is shunted to VEE via LN. The regulated voltage on the line terminal(VLN) can be calculated as: VLN=Vref+ISLPE*R9 or; VLN=Vref+[(IlineICC0.5*10-3A) Ip]*R9 where: Vref is an internally generated temperature compensated reference voltage of 3.7V and R9 is an external resistor connected between SLPE and VEE. In normal use the value of R9 would be 20. Changing the value of R9 will also affect microphone gain, DTMF gain, in control characteristics, ide-tone level, maximum output swing on LN and the dc characteristics(especially at the lower voltages). Under normal conditions, when ISLPE ! ICC+0.5mA +Ip, the static behavior of the circuit is that of a 3.7V regulator diode with an internal resistance equal to that of R9.In the audio frequency range the dynamic impedance is largely determined by R1.Fig.3 shows the equivalent impedance of the circuit.
Microphone inputs(MIC+ and MIC-) and gain pins (GAS1 and GAS2)
The UTC1062A has symmetrical inputs. Its input impedance is 64k (2*32k) and its voltage gain is typically 52 dB (when R7=68k.see Fig.13). Dynamic, magnetic, piezoelectric or electret (with built-in FET source followers) can be used. Microphone arrangements are illustrated in Fig.10. The gain of the microphone amplifier can be adjusted between 44dB and 52dB to suit the sensitivity of the transducer in use. The gain is proportional to the value of R7 which is connected between GAS1 and GAS2. Stability is ensured by the external capacitors, C6 connected between GAS1 and SLPE and C8 connected between GAS1 and VEE. The value of C6 is 100pF but this may be increased to obtain a first-order low-pass filter. The value of C8 is 10 times the value of C6. The cut-off frequency corresponds to the time constant R7*C6.
Mute input(MUTE)
A HIGH level at MUTE enables DTMF input and inhabits the microphone inputs and the receiving amplifier inputs; a LOW level or an open circuit does the reverse. Switching the mute input will cause negligible click is at the telephone outputs and on the line. In case the line current drops below 6mA(parallel operation of more sets) the circuit is always in speech condition independent of the DC level applied to the MUTE input.
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UTC1062A
Dual-tone multi-frequency input(DTMF)
LI NEAR I NTEGRATED CI RCUI T
When the DTMF input is enabled dialing tones may be sent onto the line. The voltage gain from DTMF to LN is typically 25.5dB(when R7=68k) and varies with R7 in the same way as the microphone gain. The signaling tones can be heard in the ear piece at a low level(confidence tone).
Receiving Amplifier (IR,OR and GAR)
The receiving amplifier has one input(IR) and a non-inverting output(OR). Ear piece arrangements are illustrated in Fig.11. The IR to OR gain is typically 31dB (when R4=100k). It can be adjusted between 20 and 31dB to match the sensitivity of the transducer in use. The gain is set with the value of R4 which is connected between GAR and OR. The overall receive gain, between LN and OR, is calculated by substracting the anti-sidetone network attenuation (32dB) from the amplifier gain. Two external capacitors, C4 and C7, ensure stability. C4 is normally 100pF and C7 is 10 times the value of C4. The value of C4 may be increased to obtain a first-order low-pass filter. The cut-off frequency will depend on the time constant R4*C4. The output voltage of the receiving amplifier is specified for continuous-wave drive. The maximum output voltage will be higher under speech conditions where the peak to RMS ratio is higher.
Automatic gain control input(AGC)
Automatic line loss compensation is achieved by connecting a resistor(R6) between AGC and VEE. The automatic gain control varies the gain of the microphone amplifier and the receiving amplifier in accordance with the DC line current. The control range is 5.8dB which corresponds to a line length of 5km for a 0.5mm diameter twisted pair copper cable with a DC resistance of 176/km and average attenuation of 1.2dB/km. Resistor R6 should be chosen in accordance with the exchange supply voltage and its feeding bridge resistance(see Fig.12 and Table 1). The ratio of start and stop currents of the AGC curve is independent of the value of R6. If no automatic line loss compensation is required the AGC may be left open-circuit. The amplifier, in this condition, will give their maximum specified gain.
Side-tone suppression
The anti-sidetone network, R1//Zline, R2, R3, R8, R9 and Zbal,(see Fig.4) suppresses the transmitted signal in the ear piece. Compensation is maximum when the following conditions are fulfilled: (a) R9*R2=R1[R3+(R8//Zbal)]; (b) [Zbal/(Zbal+R8)]=[Zline/(Zline+R1)]; If fixed values are chosen for R1, R2, R3 and R9 then condition(a) will always be fulfilled when R8/Zball R3. To obtain optimum side-tone suppression condition(b) has to be fulfilled which results in: Zbal=(R8/R1) Zline=k*Zline where k is a scale factor; k=(R8/R1). The scale factor (k), dependent on the value of R8, is chosen to meet following criteria: (a) Compatibility with a standard capacitor from the E6 or E12 range for Zbal, (b) Zbal//R8 R3 fulfilling condition (a) and thus ensuring correct anti-sidetone bridge operation, (c) Zbal+R8 R9 to avoid influencing the transmitter gain. In practice Zline varies considerably with the type and length. The value chosen for Zbal should therefore be for an average line length thus giving optimum setting for short or long lines. Example The balance impedance Zbal at which the optimum suppression is present can be calculated by: Suppose Zline = 210+(1265//140nF) representing a 5km line of 0.5 mm diameter, copper, twisted pair cable matched to 600 (176/km;38nF/km). When k=0.64 then R8=390,Zbal=130+(820//220nF). At line currents below 9mA the internal reference voltage is automatically adjusted to a lower value(typically 1.6V at 1mA) This means that more sets can be operated in parallel with DC line voltages (excluding the polarity guard) down to an absolute minimum voltage of 1.6V. With line currents below 9mA the circuit has limited sending and receiving levels. The internal reference voltage can be adjusted by means of an external resistor(RVA). This resistor when connected between LN and REG will decrease the internal reference voltage and when connected between REG and SLPE will increase the internal reference voltage.
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UTC1062A
LI NEAR I NTEGRATED CI RCUI T
Current(Ip) available from VCC for peripheral circuits depends on the external components used. Fig.9 shows this current for VCC 2.2V. If MUTE is LOW when the receiving amplifier is driven the available current is further reduced. Current availability can be increased by connecting the supply IC(1081) in parallel with R1, as shown in Fig.16(c), or, by increasing the DC line voltage by means of an external resistor(RVA) connected between REG and SLPE..
LN Leq Rp REG Vref C3 R9
20 4.7F
R1 VCC
C1
100F
Rp=16.2k Leq=C3*R9*Rp
VEE
Fig.3 Equivalent impedance circuit
The anti-sidetone network for the 1062 family shown in Fig.4 attenuates the signal received from the line by 32 dB before it enters the receiving amplifier. The attenuation is almost constant over the whole audio frequency range. Fig.5 shows a conventional Wheat stone bridge anti-sidetone circuit that can be used as an alternative. Both bridge types can be used with either resistive or complex set impedance.
R1
R2
Zline
R1
Zline
R2
im VEE
R9 R8
IR
R3 Rt
im VEE
R9 R8
IR
Rt
Zbal
RA SLPE
SLPE
Fig 4 Equivalent circuit of UTC1062A anti-sidetone bridge
Fig 5 Equivalent circuit of an anti-sidetone network in a wheat stone bridge configuration
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UTC1062A
Iline 150
(mA)
130
LI NEAR I NTEGRATED CI RCUI T
110
(1)
90
(2)
70
(3) (4) Tamb Ptot
50
(1) 45k 1068mW (2) 55k 934mW (3) 65k 800mW (4) 75k 666mW
2 4 6 8 10 12
30
VLN-VSLPE(V)
Fig.6 UTC1062A safe operating area
Rline
Iline
R1
ISLPE + 0.5mA
LN
VCC C1
PERIPHERAL CIRCUITS
Rexch
DC AC
0.5mA
REG
STAB
SLPE
VEE
Vexch
C3
R5
ISLPE
R9
Fig.8 Supply arrangement
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UTC1062A
2.4
LI NEAR I NTEGRATED CI RCUI T
a
Ip
(mA)
b
1.6
0.8
(a) Ip=2.1mA (b) Ip=1.7mA Iline=15mA at VLN=4V R1=620 and R9=20
0 0 1 2 3 4
Vcc(V)
5
Fig.9 Typical current Ip available from Vcc peripheral circuitry with Vcc>=2.2V. curve (a) is valid when the receiving amplifier is not driven or when MUTE =HIGH .curve(b) is valid when MUTE=LOW and the receiving amplifier is driven; Vo(rms)=150mV,RL=150.The supply possibilities can be increased simply by setting the voltage drop over the circuit VLN to a high value by means of resistor RVA connected between REG and SLPE.
7 MIC+ (1)
7 13
MIC+
VCC
7 MIC+ 6 MIC6 MIC-
VEE
9
6
MIC-
(a)
(b)
(c)
(a) Magnetic or dynamic microphone. The resistor marked(1) may be connected to decrease the terminating impedance. (b) Electret microphone. (c) Piezoelectric microphone.
Fig. 10 Alternative microphone arrangement
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UTC1062A
OR 4
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(1) OR 4
OR 4
(2)
VEE 9
VEE 9
VEE 9
(a)
(b)
(c)
(a) Dynamic ear piece. (b) Magnetic ear piece. The resistor marked(1) may be connected to prevent distortion(inductive load) (c) Piezoelectric ear piece. The ear piece marked(2) is required to increase the phase margin (capacitive load)
Fig.11 Alternative receiver arrangement
Gv (dB)
R6= 0 -2 -4 -6 0 20 40 60 80 100 120 140 Iline (mA)
R9=20 (1) R6= 78.7k
(1) (2) (3)
(2) R6= 110k (3) R6= 140k
Fig.12 Variation of gain with line current, with R6 as a parameter.
Rexch()
400
600 R6(k)
800
1000
36
100 140 D
78.7 110 D
D 93.1 120
D 82 102
Vexch(V)
48 60
Table 1 Values of resistor R6 for optimum line loss compensation, for various usual values of exchange supply voltage(Vexch) and exchange feeding bridge resistance(Rexch);R9=20
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UTC1062A
R1 620 13 10 IR VCC 7 MIC+
Vi C1 100F
LI NEAR I NTEGRATED CI RCUI T
100F OR
1
LN
4
R4 100k C4 100pF C7 1nF
RL 600 10 TO 140 mA
6 MIC11 DTMF 12 MUTE
10F
GAR GAS1
5 2
R7 68k C8 1nF C6 100pF Vo
GAS2 3 VEE REG AGC STAB SLPE
9
Vi C3 4.7F
14
R6
15 8
R5 3.6k
16
R9 20
Fig.13 Test circuit defining voltage gain of MIC+,MIC- and DTMF inputs. Voltage gain is defined as : GV=20*log(|VO/Vi|).For measuring the gain from MIC+ and MIC- the MUTE input should be LOW or opencircuit, for measuring the DTMF input MUTE should be HIGH .Inputs not under test should be open-circuit.
R1=620 13
VCC LN QR
1
C2
100F
10 IR 7 MIC+ 6 MIC11 DTMF 12
10F
4
R4 100k
ZL 600
GAR 5 C1 100F GAS1 2 GAS2 3 SLPE
C4 Vo 100pF C7 1nF R7 68k
10 TO 140 mA
C8 1nF C6 100pF
MUTE
VEE REG AGC STAB
9
Vi C3 4.7F
14
R6
15 8
R5 3.6k
16
R9 20
Fig.14 Test circuit for defining voltage gain of the receiving amplifier. Voltage gain is defined as: GV=20*log(|VO/Vi|).
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UTC1062A
R10 130
BAS11 (x2) BZX79 C12
LI NEAR I NTEGRATED CI RCUI T
R1 620 R2 132k C5 100nF 10 IR 1 LN 13 VCC
C1 100F
Telephone Line
C2
BZW14 (x2)
4
R3 3.92k
R4 C4 100pF
OR DTMF
11 From dial and control circuits
12
5 GAR 7
UTCI062A
MUTE
C7 1nF
6
MIC+ MICSLPE 16 GAS1 2 GAS2 3 REG 14 AGC 15
R8 390
C6 100pF
STAB VEE 8 9
R7 RVA(R16.R14) R5 3.6k
Zbal
R9 20
C8 1nF
C3 4.7F
R6
Fig.15 Typical application of the UTC1062A ,shown here with a piezoelectric ear piece and DTMF dialing. The bridge to the left ,the Zener diode and R10 limit the current into the circuit and the voltage across the circuit during line transients. Pulse dialing or register recall required a different protection arrangement. The DC line voltage can be set to a higher value by resistor RVA(REG to SLPE).
LN
VCC DTMF
VDD DTMF
CARDLE CONTRAT
UTC1062A
MUTE VEE
dialling circuit
M1 VSS DP/FL
TELEPHONE LINE
BSN254A
Fig.16 Typical applications of the UTC1062A (simplified) The dashed lines show an optional flash ( register recall by timed loop break).
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